1. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 1 Project: IEEE P802.15 Working Group for Wireless Personal Area Networks (WPANs) Submission Title: [Merged UWB proposal for IEEE 802.15.4a Alt-PHY ] Date Submitted: [14 Mar 2005] Source: [(1) Andy Molisch, (2) Francois Chin] Company: [(1) MERL, 201 Broadway, Boston, USA, (2) Institute for Infocomm Research, Singapore] Voice: [(1) +1 617 621 7500, (2) +65-68745687] E-Mail: [(1) molisch@merl.com (2) chinfrancois@i2r.a-star.edu.sg] Re: [Response to the call for proposal of IEEE 802.15.4a, Doc Number: 15-04-0380-02-004a ] Abstract:[Merged Proposal to IEEE 802.15.4a Task Group] Purpose:[For presentation and consideration by the IEEE802.15.4a committee] Notice:This document has been prepared to assist the IEEE P802.15. It is offered as a basis for discussion and is not binding on the contributing individual(s) or organization(s). The material in this document is subject to change in form and content after further study. The contributor(s) reserve(s) the right to add, amend or withdraw material contained herein. Release:The contributor acknowledges and accepts that this contribution becomes the property of IEEE and may be made publicly available by P802.15.

2. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 2 Authors Institute for Infocomm Research: Francois Chin, Xiaoming Peng, Sam Kwok, Zhongding Lei, Kannan, Yong-Huat Chew, Chin-Choy Chai, Rahim, Manjeet, T.T. Tjhung, Hongyi Fu, Tung-Chong Wong General Atomics: Naiel Askar, Susan Lin Thales & Cellonics: Serge Hethuin, Isabelle Bucaille, Arnaud Tonnerre, Fabrice Legrand, Joe Jurianto KERI & SSU & KWU: Kwan-Ho Kim, Sungsoo Choi, Youngjin Park, Hui- Myoung Oh, Yoan Shin, Won cheol Lee, and Ho-In Jeon Create-Net & China UWB Forum: Zheng Zhou, Frank Zheng, Honggang Zhang, Xiaofei Zhou, Iacopo Carreras, Sandro Pera, Imrich Chlamtac Staccato Communications: Roberto Aiello, Torbjorn Larsson Wisair: Gadi Shor, Sorin Goldenberg

3. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 3 Authors CWC:Ian Oppermann, Alberto Rabbachin AetherWire:Mark Jamtgaard, Patrick Houghton CEA-LETI: Laurent Ouvry, Samuel Dubouloz, Sébastien de Rivaz, Benoit Denis, Michael Pelissier, Manuel Pezzin et al. STMicroelectronics: Gian Mario Maggio, Chiara Cattaneo, Philippe Rouzet & al. MERL: Andreas F. Molisch, Philip Orlik, Zafer Sahinoglu Harris: Rick Roberts Time Domain: Vern Brethour, Adrian Jennings French Telecom R&D: Patricia Martigne, Benoit Miscopein, Jean Schwoerer

4. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 4 Proposal Main Features 1.Impulse-radio based (pulse-shape independent) 2.Support for different receiver architectures (coherent/non- coherent) 3.Flexible modulation format 4.Support for multiple rates 5.Enables accurate ranging/positioning 6.Support for multiple SOP

5. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 5 Motivation: Supports homogenous and heterogeneous network architectures Different classes of nodes, with different reliability requirements (and cost) must inter-work

6. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 6 UWB Technology Impulse-Radio (IR) based: –Very short pulses  Reduced ISI –Robustness against fading –Episodic transmission (for LDR) allowing long sleep-mode periods and energy saving Low-complexity implementation

7. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 7 Modulation Features Simple, scalable modulation format Flexibility for system designer Modulation compatible with multiple coherent/non-coherent receiver schemes

8. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 8 Types of Receivers Supported Coherent Detection: The phase of the received carrier waveform is known, and utilized for demodulation Differential Chip Detection: The carrier phase of the previous signaling interval is used as phase reference for demodulation Non-coherent Detection: The carrier phase information (e.g.pulse polarity) is unknown at the receiver

9. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 9 Pros (+) and cons (-) of RX architectures: Coherent + : Sensitivity + : Use of polarity to carry data + : Optimal processing gain achievable - : Complexity of channel estimation and RAKE receiver - : Longer acquisition time Differential (or using Transmitted Reference) + : Gives a reference for faster channel estimation (coherent approach) + : No channel estimation (non-coherent approach) - : Asymptotic loss of 3dB for transmitted reference (not for DPSK) Non-coherent + : Low complexity + : Acquisition speed - : Sensitivity, robustness to SOP and interferers

10. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 10 Overview Basic waveform that simultaneously supports demodulation by either coherent or non-coherent receiver – Non-coherent receiver can use either 2-PPM or OOK demodulation – Coherent receiver can also resolved phase of pulse and benefits from additional coding gain – Differential / Transmit reference (TR) receiver can get information form phase difference between data pulse and reference pulse Main idea: – Common preamble signaling for different classes of nodes / type of receivers (coherent / differential / non-coherent)

11. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 11 Chip rate24 Mcps ** # Pulse / Chip Period1 Pulse Rep. Freq.24 MHz # Chip / symbol (Code length)32 Symbol Rate24/32 MHz = 0.75 MSps info. bit / sym (Mandatory Mode)4 bit / symbol Mandatory bit rate4 bit/sym x 0.75 MSps = 3 Mbps #Code Sequences/ piconet16 (4 bit/symbol) Orthogonal Sequence Keying Modulation{+1,-1, 0} ternary pulse train / {+1,-1} bipolar Total # simultaneous piconets supported 6 per FDM band Multple access for piconetsFixed sequence & FDM band for each piconet Example System Parameters ** To be determined

12. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 12 Multiple access Multiple access within piconet: TDMA+CSMA/CA same as 15.4 Multiple access across piconets: CDM + FDM Different Piconet uses different Base Sequence & different 500 MHz band

13. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 13 Realization #1

14. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 14 System Description Each piconet uses one set of code sequences for different classes of nodes / type of receivers (coherent / differential / non-coherent receivers) 16 Orthogonal Sequences of code length 32 to represent a 4-bit symbol PRF (chip rate): 24 MHz (TBD) – Low enough to avoid significant interchip interference (ICI) with all 802.15.4a multipath models – High enough to ensure low pulse peak power FEC: optional (or low complexity type)

15. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 15 Criteria of Code Sequence Design 1.The sequence Set should have orthogonal (or near orthogonal) cross correlation properties to minimise symbol decision error for all the below receivers a.For coherent receiver b.For differential chip receiver c.For transmitted reference receiver d.For non-coherent symbol detection receiver e.Energy detection receiver 2.Each sequence should have good auto-correlation properties

16. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 16 Base Sequence Set Seq 10 + - - 0 0 0 + - 0 + + + 0 + 0 - 0 0 0 0 + 0 0 - 0 - + 0 0 - - Seq 20 - 0 + - - 0 0 0 + 0 + 0 + - 0 + 0 0 0 0 + - 0 0 + 0 0 + - - - Seq 30 - + 0 + + - - - 0 + 0 0 0 - 0 0 - 0 + 0 + + 0 0 0 0 - + - 0 0 Seq 40 0 + 0 + - - 0 - - 0 0 0 - + - + + 0 0 + + 0 - 0 0 + 0 0 0 0 - Seq 50 + - + - 0 0 - 0 0 + + 0 0 0 0 + 0 - - 0 - 0 + 0 0 0 - - + 0 + Seq 60 0 0 - + - 0 0 0 0 + + 0 + 0 - 0 0 - 0 0 0 + 0 - - - + + 0 + - 31-chip Ternary Sequence set are chosen Only one sequence and one fixed band (no hopping) will be used by all devices in a piconet Logical channels for support of multiple piconets 6 sequences = 6 logical channels (e.g. overlapping piconets) for each FDM Band The same base sequence will be used to construct the symbol-to- chip mapping table

17. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 17 SymbolCyclic shift to right by n chips, n= 32-Chip value 000000 + - - 0 0 0 + - 0 + + + 0 + 0 - 0 0 0 0 + 0 0 - 0 - + 0 0 - - 000120 - - + - - 0 0 0 + - 0 + + + 0 + 0 - 0 0 0 0 + 0 0 - 0 - + 0 0 001140 0 0 - - + - - 0 0 0 + - 0 + + + 0 + 0 - 0 0 0 0 + 0 0 - 0 - + 001060 - + 0 0 - - + - - 0 0 0 + - 0 + + + 0 + 0 - 0 0 0 0 + 0 0 - 0 011080 – 0 - + 0 0 - - + - - 0 0 0 + - 0 + + + 0 + 0 - 0 0 0 0 + 0 0 0111100 0 0 – 0 - + 0 0 - - + - - 0 0 0 + - 0 + + + 0 + 0 - 0 0 0 0 + 0101120 0 + 0 0 – 0 - + 0 0 - - + - - 0 0 0 + - 0 + + + 0 + 0 - 0 0 0 0100140 0 0 0 + 0 0 – 0 - + 0 0 - - + - - 0 0 0 + - 0 + + + 0 + 0 – 0 1100150 0 0 0 0 + 0 0 – 0 - + 0 0 - - + - - 0 0 0 + - 0 + + + 0 + 0 – 1101170 0 – 0 0 0 0 + 0 0 – 0 - + 0 0 - - + - - 0 0 0 + - 0 + + + 0 + 1111190 0 + 0 – 0 0 0 0 + 0 0 – 0 - + 0 0 - - + - - 0 0 0 + - 0 + + + 1110210 + + 0 + 0 – 0 0 0 0 + 0 0 – 0 - + 0 0 - - + - - 0 0 0 + - 0 + 1010230 0 + + + 0 + 0 – 0 0 0 0 + 0 0 – 0 - + 0 0 - - + - - 0 0 0 + - 1011250 + - 0 + + + 0 + 0 – 0 0 0 0 + 0 0 – 0 - + 0 0 - - + - - 0 0 0 1001270 0 0 + - 0 + + + 0 + 0 – 0 0 0 0 + 0 0 – 0 - + 0 0 - - + - - 0 1000290 - 0 0 0 + - 0 + + + 0 + 0 – 0 0 0 0 + 0 0 – 0 - + 0 0 - - + - Symbol-to-Chip Mapping: Gray coded 16-ary Ternary Orthogonal Keying To obtain 32-chip per symbol, cyclic shift the Base Sequence first, then append a ‘0’-chip in front

18. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 18 Modulation & Coding (Mode 1) Mode 1- common signaling for all receivers (e.g. Beacon) Bit to symbol mapping: group every 4 bits into a symbol Symbol-to-chip mapping: Each 4-bit symbol is mapped to one of 16 32-chip sequence, according to 16-ary Ternary Orthogonal Keying Symbol Repetition: for data rate and range scalability Pulse Genarator: Transmit Ternary pulses at PRF = 24MHz (TBD) Bit-to- Symbol Repetition Binary data From PPDU Pulse Generator {0,1,-1} Ternary Sequence Symbol- to-Chip

19. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 19 Modulation & Coding (Mode 2) Mode 2 – for enhanced performance when receiver types are known (except for energy detector) Bit to symbol mapping: group every 4 bits into a symbol Symbol-to-chip mapping: Each 4-bit symbol is mapped to one of 16 32-chip sequence, according to 16-ary Ternary Orthogonal Keying Symbol Repetition: for data rate and range scalability Ternary to Binary conversion: (-1/+1 → 1,0 → -1) Pulse Genarator: Transmit bipolar pulses at PRF = 24MHz (TBD) Bit-to- Symbol Repetition Binary data From PPDU Ternary- Binary {0,1,-1} Ternary Sequence Symbol- to-Chip Pulse Generator {1,-1} Binary Sequence

20. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 20 Code Sequence Properties & Performance 1.AWGN Performance 2.Multipath Performance (in Appendix) I.For Coherent Symbol Detector II.For Non-coherent Symbol Detector III.For Differential Chip Detector IV.For Energy Detector

21. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 21 AWGN Performance AWGN performance @ 1% PER @ 3 MbpsCoherent symbol detection Non-coherent symbol detection Differential chip detection Energy detection Mode 16.5 dB8.5 dB13 dB13.5 dB Mode 26.5 dB7.5 dB11.5 dB-

22. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 22 Summary The proposed system: Impulse-radio based system coupled with a Common ternary signaling allows operation among different classes of nodes / type of receivers, with varying cost / power / performance trade-off Is robust against multipath and SOP interference

23. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 23 Realization #2

24. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 24 X 1 = 0, X 2 = 0 X 1 = 1, X 2 = 1 X 1 = 1, X 2 = 0 X 1 = 0, X 2 = 1 Non-coherent receiver only sees position – Demodulates only x 1 – No Viterbi decoding required (easy since x 1 =b k ) – Achieves no coding gain, assumes b k = x 1  Done. Coherent receiver demodulates position and phase – Decodes x 1 & x 2 – Viterbi decoding used to estimate original bit, b k – Achieves coding gain of original rate ½ code Non-Coherent and Coherent Demodulation

25. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 25 Encoding two coded bits requires a 4-point signal constellation – Each axis represents one of two possible positions (orthogonal axes) – Phase of pulse determines sign of constellation point on axis  4-BOK Non-coherent receiver is insensitive to phase – see only two points in constellation  2-PPM Support for OOK receiver is possible by demodulating only one of the two dimensions (i.e. just look at first position: pulse or not?) OOK constellation 2-PPM constellation 2-PPM constellation 4-BOK (coherent) constellation Non-coherent receiver cannot see these

26. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 26 Transmitted Reference (TR) TR schemes simplify the channel estimation process Reference waveform available for synchronisation Potentially more robust (than non-coherent) under SOP operation Supports both coherent/differentially-coherent demodulation Multiple pulses can be used to increase throughput Implementation challenges: – Analogue: Implementing delay value, – delay mismatch, jitter

27. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 27 TsTs Differential Encoding of Bits +1 -1 +1 -1 +1 -1 -1 -1 +1 +1 -1 -1 0 0 1 1 0 0 1 b0b0 b4b4 b3b3 b2b2 b1b1 b5b5 b -1 Tx Bits Reference Polarity

28. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 28 Multiple access On top of this modulation scheme: – Polarity hopping: repeat data at regular intervals, but encoded with polarity sequence that is unique for piconet – Alternatives: Time hopping Ternary encoding sequence Note that PPM can be applied on a “per pulse” basis or a “per symbol” basis (see 05- 0130 and Backup slides)

29. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 29 Symbol Format (1 st realization) Positive pulse Negative pulse Non-coherent receiver sees energy in one of the two halves Differentially coherent receiver sees phase differences Coherent receiver sees symbols drawn from 2-D signal space: TdTd TfTf TsTs TcTc

30. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 30 Bandwidth Usage Flexible use of (multi-)bands Signal bandwidth may be 500 MHz to 2 GHz Bandwidth may change depending on application and regulatory environment Use of polarity randomization for spectral smoothing Different bandwidth use options being considered

31. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 31 Band Plan BAND_IDLower frequencyCenter frequencyUpper frequency 13168 MHz3432 MHz3696 MHz 2 3960 MHz4224 MHz 3 4488 MHz4752 MHz 4 5016 MHz5280 MHz 5 5544 MHz5808 MHz 6 6072 MHz6336 MHz 7 6600 MHz6864 MHz 8 7128 MHz7392 MHz 9 7656 MHz7920 MHz 107920 MHz8184 MHz8448 MHz 118448 MHz8712 MHz8976 MHz 128976 MHz9240 MHz9504 MHz 139504 MHz9768 MHz10032 MHz 1410032 MHz10296 MHz10560 MHz

32. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 32 Option: Linear Pulse Combination Spectral shaping by linear combination of delayed, weighted pulses – Adaptive determination of weight and delay – Number of pulses and delay range restricted – Can adjust to interferers at different distances (required nulldepth) and frequencies Weight/delay adaptation in two-step procedure Initialization as solution to quadratic optimization problem (closed-form) Refinement by back-propagating neural network Matched filter at receiver  good spectrum helps coexistence and interference suppression

33. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 33 Spectral Shaping & Polarity Scrambling T d = 10 ns T d = 20 ns W/ Polarity ScramblingW/O Polarity Scrambling

34. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 34 Adaptive Frame Duration Advantage of large number of pulses per symbol: – Smaller peak-to-average ratio – Increased possible number of SOPs Disadvantage: – Increased inter-frame interference – In TR: also increased interference from reference pulse to data pulse Solution: adaptive frame duration – Feed back delay spread and interference to transmitter – Depending on those parameters, TX chooses frame duration

35. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 35 Ranging

36. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 36 Ranging Motivation : – Benefit from high time resolution (thanks to signal bandwidth): Theoretically: 2GHz provides less than 20cm resolution Practically: Impairments, low cost/complexity devices should support ~50cm accuracy with simple detection strategies (better with high resolution techniques) Approach : – Use Two Way Ranging between 2 devices with no network constraint (preferred); no need for time synchronization among nodes – Use One Way Ranging and TDOA under some network constraints (if supported) TOF : Time Of Flight RTT : Round Trip Time SHR : Synchronization Header Asynchronous Ranging

37. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 37 TOA Delay Estimation - Non-Coherent Use bank of integrators to determine coarse synchronisation “uncertainty” region – Symbol synchronisation “uncertainty” region given by coarse synchronisation ( e.g., 4ns-20ns) A refinement search is applied onto the uncertainty region by either – further dividing it into narrower non overlapping regions for non-coherent refinement (e.g., 1ns –> 4ns) or – Coherent search with a template correlation Energy Analyzer Integrator outputs Leading Edge Search Refinement Performed within the selected uncertainty region Detects the coarse “uncertainty region” Range info T RB : the length of uncertainty region

38. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 38 TOA Delay Estimation - Non-Coherent (cont’d) The algorithm selects the maximum value integration window index and then it searches backward to find the first integration value which crosses an adaptively set threshold. If there are no values crossing the threshold, the peak position is used for the TOA estimation. Actual TOA MES based TOA Estimate Strongest Path, energy block Contains leading edge Threshold based TOA Estimate Threshold Searchback window MES-SB based TOA Estimate MES: Maximum Energy Search TC: Threshold comparison SB: Search Back 0 1 2 N

39. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 39 Features - Sequential two-way ranging is executed via relay transmissions - PAN coordinator manages the overall schedule for positioning - Inactive mode processing is required along the positioning - PAN coordinator may transfer all sorts of information such as observed - TDOAs to a processing unit (PU) for position calculation Benefits - It does not need pre-synchronization among the devices - Positioning in mobile environment is partly accomplished PAN coordinator P_FFD1 P_FFD2 P_FFD3 RFD TOA 14 TOA 24 TOA 34 P_FFD : Positioning Full Function Device RFD : Reduced Function Device PU Proposed Positioning Scheme

40. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 40 Process of Proposed Positioning Scheme TOA measurement

41. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 41 More Details for obtaining TDOAs Distances among the positioning FFDs are calculated from RTT measurements and known time interval T Using observed RTT measurements and calculated distances, TOAs/TDOAs are updated RTT 12 = T + 2T 12 RTT 23 = T + 2T 23 RTT 13 = T 12 + 2T + T 23 + T 13 T 12 = (RTT 12 – T)/2 T 23 = (RTT 23 – T)/2 T 13 = (RTT 13 – T 12 – T 23 – 2T) RTT 34 = T 34 + T + T 34 RTT 14 = T 12 + T + T 23 + T + T 34 + T + T 14 RTT 24 = T 23 + T + T 34 + T + T 24 TOA 14 = (RTT 14 - T 12 - T 23 - TOA 34 - 3T) TOA 34 = (RTT 34 - T)/2 TOA 24 = (RTT 24 - T 23 - TOA 34 - 2T) TDOA 12 = TOA 14 – TOA 24 TDOA 23 = TOA 24 – TOA 34

42. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 42 Position Calculation using TDOAs The range difference measurement defines a hyperboloid of constant range difference When multiple range difference measurements are obtained, producing multiple hyperboloids, the position location of the device is at the intersection among the hyperboloids

43. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 43 Conclusions Proposal based upon UWB impulse radio – High time resolution suitable for precise ranging using TOA – Modulation: Pulse-shape independent Robust under SOP operation Facilitates synchronization/tracking Supports multiple coherent/non-coherent RX architectures System tradeoffs – Modulation optimized for several aspects (requirements, performances, flexibility, technology) – Trade-off complexity/performance RX Flexible implementation of the receiver – Coherent, differential, non-coherent (energy collection) – Analogue, digital Fits with multiple technologies – Easy implementation in CMOS – Very low power solution (technology, architecture, system level)

44. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 44 Backup slides

45. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 45 PER in 15.4a Channel Model Non-Coherent (Energy Collection) BPPM Framing format: Preamble (32 bits) SFD (8 bits) LEN MHR+MSDU (240 bits) CRC (16 bits) Simulations over 1000 channel responses BW = 2GHz – Integration Time = 80ns Implementation loss + Noise figure margin : 11 dB Max range is determined from:  Required Eb/N0,  Implementation margin  Path loss characteristics X1 (CM8)X2 (CM1)X3 (CM5)X4 (CM9) Required Eb/N019.5 dB20 dB21 dB21.5 dB Max Range (I)10.78 m84.61 m86.72 m58.67 m Max Range (II)7.33 m53.25 m54.15 m34.72 m Case I: 250 kbps – PRP 250 ns with 16 pre-integrations = 4 µs Case II: 250 kbps – PRP 500 ns with 8 post-integrations

46. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 46 PER/BER in 15.4a Channel Model DBPSK (RAKE) X1 (CM8)X2 (CM1)X3 (CM5)X4 (CM9) Required Eb/N018 dB17.5 dB18.5 dB Max Range (I)12.66 m116.70 m120.27 m90.84 m Max Range (II)9.18 m79.34 m81.23 m58.67 m Implementation loss and Noise figure margin : 11 dB Theoretical BER Curves – Integration Time = 50 ns Case I: 250 kbps – PRP 250 ns with 16 pre-integration = 4 µs Case II: 250 kbps – PRP 500 ns with 8 post-integrations

47. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 47 Link Budget: Non-Coherent (Energy Collection) BPPM Parameter Mandatory Value (PRP = 4 µs) Optional Value (PRP = 500ns - 8 integrations) Peak Payload bit rate (R b )250 kb/s Average Tx Power Gain (P T )-10.64 dBm Tx antenna gain (G T )0 dBi f’c: (geometric frequency)3.873 GHz Path Loss @ 1m: L 1 = 20log10(4. .f’ c / c) 44.20 dB Path Loss @ d m: L 2 = 20log10(d)29.54 dB @ d = 30 m Rx Antenna Gain (G R )0 dBi Rx Power (P R = P T + G T + G R – L 1 – L 2 )-84.38 dBm Average noise power per bit: N = -174 + 10log 10 (Rb)-120.02 dBm Rx noise figure (N F )7 dB Average noise power per bit (P N = N + N F )-113.02 dBm Minimum E b /N 0 (S)14 dB17.6 dB Implementation Loss (I)5 dB Link Margin (M = P R - P N – S – I)9.64 dB6.04 dB Proposed Min. Rx Sensitivity Level-94.02 dBm-90.42 dBm

48. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 48 Link Budget: DBPSK (RAKE) Parameter Mandatory Value (PRP = 4 µs) Optional Value (PRP = 500ns - 8 integrations) Peak Payload bit rate (R b )250 kb/s Average Tx Power Gain (P T )-10.64 dBm Tx antenna gain (G T )0 dBi f’c: (geometric frequency)3.873 GHz Path Loss @ 1m: L 1 = 20log10(4. .f’ c / c) 44.20 dB Path Loss @ d m: L 2 = 20log10(d)29.54 dB @ d = 30 m Rx Antenna Gain (G R )0 dBi Rx Power (P R = P T + G T + G R – L 1 – L 2 )-84.38 dBm Average noise power per bit: N = -174 + 10log 10 (Rb)-120.02 dBm Rx noise figure (N F )7 dB Average noise power per bit (P N = N + N F )-113.02 dBm Minimum E b /N 0 (S)13 dB16 dB Implementation Loss (I)5 dB Link Margin (M = P R - P N – S – I)10.64 dB7.64 dB Proposed Min. Rx Sensitivity Level-95.02 dBm-92.02 dBm

49. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 49 Framing – 802.15.4 Compatible CAPCFPIPBP Beacon Interval BP : Beacon Period CAP : Contention Access Period CFP : Contention Free Period IP : Inactive Period (optional) Superframe Duration Beacon slotCAP slotCFP slot 0123456789101112131415 PreambleSFDPSDU = MPDUPHY layer PPDU (PHY Protocol Data Unit) PSDU (PHY Service Data Unit)SHR Octets 3241 Frame length PHR 1

50. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 50 Throughput PreambleSFDPSDU = MPDUPHY layer PPDU (PHY Protocol Data Unit) PSDU (PHY Service Data Unit)SHR Bytes 3241 Frame length PHR 1 PreambleSFDPSDUPHY layer PPDU (PHY Protocol Data Unit) PSDUSHR Bytes 541 Frame length PHR 1 Data Frame (32 octet PSDU)ACK Frame (5 octet PSDU) TdataTackT_ACK Numerical example (high-band) Preamble + SFD + PHR = 6 octets Tdata = 1.216 ms T_ACK = 50  s (turn around time requested by IEEE 802.15.4 is 192  s) Tack = 0.352 ms IFS = 100 μs  Throughput = 32 octets/1.718 ms = 149 kb/s  Average data-rate at receiver PHY-SAP 250 kb/s (Basic Mode) IFS

51. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 51 Saving Power Power Saving techniques achieved by combining advantages offered at 3 levels: – Technology (best if CMOS) – Architecture (flexible schemes provided by the TH+pulse modulation) – System level (framing, protocol usage) Selected techniques used in one existing realization (see proof of concept slides) – Low-duty cycle Episodic transmission/reception Scheduled wake-up 80  s RTOS tick – Ad-hoc networking using multi-hop Special rapid acquisition codes / algorithm Matchmaking further reduces acquisition time – Multi-stage time-of-day clock Synchronous counter / current mode logic for highest speed stages Ripple counter / static CMOS for lowest speed stages – Compute-intensive correlation done in hardware

52. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 52 ENERGY Spread in CM1 PDF of TOA estimation errors are illustrated for MES at various E b N 0 – CM1, integration interval 4ns, Tf=200ns (results will be updated for Tf=240ns)

53. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 53 Ranging Simulation Settings Notations and TermsDefinitionValue in Simulations TfTf Pulse repetition interval, frame200ns NbNb Number of blocks within a T f 50 NcNc Number of refinement intervals within a T f 400 TH{}Time hopping sequence in chips{h1,...., h5} POL{}Polarity codes{p1,..., p5} N1N1 Number of frames in the 1st-step50 N2N2 Number of frames in the refinement30 BWBandwidth2GHz CNumber of correlators (refinement stage)10 Note: Results are to be provided when T f is set to 240ns.

54. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 54 Ranging Results IEEE 802.15.4a CM1-Residential LOS Round Trip ranging error (with no drift compensation) – ~16cm (0.088ms), no clock drift – ~17.1cm (1ppm) – ~20.1cm (4ppm) – ~26cm (10ppm) – ~56cm (40ppm) True Distance (m)One-way ranging error (confidence level) 25 m 8 cm ( 97 %) 30 m 8 cm (~ 90 %)

55. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 55 Two Way Ranging (TWR) Main Limitations / Impact of Clock Drift on Perceived Time Range estimation is affected by : Relative clock drift between A and B Prescribed response delay Clock accuracy in A and B Channel response (weak direct path) Is the frequency offset relative to the nominal ideal frequency Simple immediate TWR made unusable with reasonnable crystal accuracies. Solution is : Performing fine drift estimation/compensation Benefiting from cooperative transactions (estimated clock ratios …) 250 kbps, 38 bytes PPDU 500 kbps, 9 bytes PPDU  f/f \ Treply (max error) 1408  s1226  s336  s154  s 4 ppm1.69 m1.47 m0.40 m0.18 m 25 ppm10.56 m9.19 m2.52 m1.15 m 40 ppm16.9 m14.7 m4.0 m1.8 m Example using Imm-ACK SIFS of 15.4 and 15.3 of respectively 192us and 10 us and PPDU size of respectively 38 and 9 bytes

56. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 56 Antenna Feasibility Capacitive Dipole and Various Bowtie Antennas Bowtie antenna 55 mm 40 mm

57. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 57 “Proof-of-Concept” (1) Non-coherent Transceiver 5 Mbps BPPM 350 ps pulse train with long scrambling code Non-coherent, Energy Collection Receiver

58. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 58 “Proof-of-Concept” (2) Non-coherent Transceiver UWB Transmitter 400 μm x 400 μm 0.35 μm CMOS UWB Transceiver Test architecture <10 mm 2 0.35 μm SiGe Bi-CMOS UWB-IR BPPM Non-Coherent Transceiver Implementation

59. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 59 “Proof-of-Concept” (3): Transmitter - Lower Band UWB Transmitter chip for generating impulse doublets Delay Buffers N-C N-Channel Drivers P-Channel Drivers

60. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 60 “Proof-of-Concept” (4): Receiver - Lower Band Coherent UWB Receiver with multiple time integrating correlators 32 Time-Integrating Correlators PLL Loop Filter VGC Amp Code Sequence Generators LF RTC DACs “Rails” for testing analog circuits DACs High-Frequency Real Time Clock

61. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 61 “Proof-of-Concept” (5) High Speed Coherent Circuit Elements 3-5 GHz LNA Chip and layout 20 GHz digitizer for UWB 20 GHz DLL for UWB RF front end chips in CMOS 0.13  m, 1.2V

62. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 62 Backup Slides

63. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 63 Synchronisation Preamble Code sequences has good autocorrelation properties Preamble is constructed by repeating ‘0000’ symbols Long preamble is constructed by further symbol repetition Correlator output for synchronisation

64. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 64 Frame Format PPDU Octets: PHY Layer Preamble 4? 1 Frame Length SFD 1 SHRPHRPSDU MPDU Data: 32 (n=23) Frame Cont. Seq. #Address Data Payload CRC Octets: 210/4/82 MAC Sublayer n MHRMSDUMFR For ACK: 5 (n=0)

65. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 65 Code Sequence Properties & Performance 1.AWGN Performance 2.Multipath Performance (in Appendix) I.For Coherent Symbol Detector II.For Non-coherent Symbol Detector III.For Differential Chip Detector IV.For Energy Detector

66. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 66 Auto Correlation Properties for Coherent/Non-Coherent Symbol Detector

67. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 67 TxSeqSet * RxSeqSet' (Mode 2) =TxSeqSet * RxSeqSet' (Mode 1) = Cross Correlation Properties for Coherent/Non-Coherent Symbol Detector

68. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 68 Multipath Performance for Coherent Symbol Detector

69. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 69 Multipath Performance for Non-Coherent Symbol Detector

70. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 70 Auto Correlation Properties for Differential Chip Detector

71. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 71 Cross Correlation Properties for Differential Chip Detector DifferentialChip(TxSeqSet) * DifferentialChip(RxSeqSet)’ (Mode 1) = DifferentialChip(TxSeqSet) * DifferentialChip(RxSeqSet)’ (Mode 2) =

72. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 72 Multipath Combining for Differential Chip Detector

73. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 73 Multipath Performance for Differential Chip Detector Simulation Results to be available later

74. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 74 Energy detection technique rather than coherent receiver, for low cost, low complexity Soft chip values gives best results Oversampling & sequence correlation is used to recovery chip timing recovery Synchronization fully re-acquired for each new packet received (=> no very accurate timebase needed) BPF( ) 2 LPF / integrator ADC Sample Rate 1/T c Soft Despread Non-Coherent Receiver Architectures (Mode 1)

75. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 75 Auto Correlation Properties for Energy Detection Receiver

76. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 76 Cross Correlation Properties for Energy Detection Receiver TxSeqSet * RxSeqSet ' =

77. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 77 Multipath Performance for Energy Detector

78. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 78 Basic Data Rate Throughput (Low Rate Modes) Useful data rate calculation for 32 byte PSDU (Xo = 0.75 Mbps) Symbol Period = 1.33us –Data frame time : 38 x 8 / 0.75= 405.3 µsec –ACK frame time : 11 x 8 / 0.75 = 117.3 µsec –t ACK (considering 15.4 spec) : 192 µsec –LIFS (considering 15.4 spec) : 640 µsec –T frame = 1355 µsec –Useful Basic Data Rate = 189.0 kbps

79. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 79 Basic Data Rate Throughput (High Rate Modes) Useful data rate calculation for 32 byte PSDU (Xo = 3 Mbps) Symbol Period = 1.33us –Data frame time : 38 x 8 / 3 = 101.3 µsec –ACK frame time : 11 x 8 / 3 = 29.3 µsec –t ACK (considering 15.4 spec) : 192 µsec –LIFS (considering 15.4 spec) : 640 µsec –T frame = 963 µsec –Useful Basic Data Rate = 265.9 kbps

80. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 80 Basic Data Rate Throughput (High Rate Modes) Useful data rate calculation for 127 byte PSDU (Xo = 3 Mbps) Symbol Period = 1.33us –Data frame time : 127 x 8 / 3 = 354.7 µsec –ACK frame time : 11 x 8 / 3 = 29.3 µsec –t ACK (considering 15.4 spec) : 192 µsec –LIFS (considering 15.4 spec) : 640 µsec –T frame = 1216 µsec –Useful Basic Data Rate = 853.5 kbps

81. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 81 Link Budget

82. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 82 BER Performance in AWGN Channel MRC Solution (coherent) Differential Solution Energy Collection solution in OOK Transmitted Reference (one pulse) -3 dB : the “reference” is not in the same PRP ! PER = 1% with 32 bytes PSDU  acceptable BER 4x10 -5 with no channel coding

83. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 83 Positioning Scenario Overview

84. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 84 Positioning Scenario Overview Cluster 1  Case 1  Case 2 PAN Coordinator FFD RFD Positioning FFD(P_FFD) Using static reference nodes in relatively large scaled cluster : –Power control is required –Power consumption increases –All devices in cluster must be in inactive data transmission mode Using static and dynamic nodes in overlapped small scaled sub- clusters : –Sequential positioning is executed in each sub-cluster –Low power consumption –Associated sub-cluster in positioning mode should be in inactive data transmission mode

85. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 85 Positioning Scenario for Star topology Star topology –PAN coordinator activated mode Positioning all devices Re-alignment of positioning FFD’s list is not required –Target device activated mode Positioning is requested from some device Re-alignment of positioning FFD’s list is required

86. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 86 Positioning Scenario for Cluster-tree Topology Cluster-tree topology

87. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 87 Ranging Accuracy Improvement Technical requirement for positioning –“It can be related to precise (tens of centimeters) localization in some cases, but is generally limited to about one meter ” Parameters for technical requirement –Minimum required pulse duration : –Minimum required clock speed for the correlator in the conventional coherent systems ★ Fast ADC clock speed in the conventional coherent receiver is required for the digital signal processing High Cost !

88. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 88 Analog Energy Window Bank (1) Digital signal processing with fast clock can be replaced by using analog energy window bank with low clock speed Why analog energy window bank? –Conventional single energy window may support the energy detection for data demodulation in the operation mode –However, this cannot guarantee the correct searching of the signal position in the timing mode (that also means the ambiguity of ranging accuracy) Analog energy window bank can sufficiently support timing and calibration as well as operation mode –Widow Bank Size : ~4 nsec (smallest pulse duration) –The number of energy windows in a bank : 11 –Operation clock speed of each energy window : 24 MHz –Number of the required energy windows depends on the power delay profile of the multipath channel (effective multipath components)

89. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 89 Analog Energy Window Bank (2) Size of the Integrated Bank (S) First Path Estimation and Calibration

90. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 90 Modifying MAC

91. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 91 Modifications of MAC Command Frame (1) Features –Frame control field frame type : positioning (new addition using a reserved bit) –Command frame identifier field Positioning request/response (new addition) –Positioning parameter information field Absolute coordinates of positioning FFDs POS range List of positioning FFDs and target devices Power control Pre-determined processing time (T) Octets : 2 10/4/81variable2 Frame controlSequencenumberAddressingfields command frame identifier Positioning parameterCommandpayloadFCS MHR MAC payload MFR

92. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 92 Modifications of MAC Command Frame (2) Command frame identifier 0x01 Association request 0x02 Association response 0x03 Disassociation notification 0x04 Data request 0x05 PAN ID conflict notification 0x06 Orphan notification 0x07 Beacon request 0x08 Coordinator realignment 0x09 GTS request 0x0a Positioning request 0x0b Positioning response 0x0c~0xff Reserved bits : 0~2 34567~910~1112~1314~15FrametypeSecurityenabledFramependingAck.request Intra- PAN ReservedDest. addressing mode ReservedSource Frame type value Description000Beacon 001Data 010Acknowledgment 011 MAC command 100Positioning 101~111Reserved Frame Control Command frame identifier Positioning parameterFixedcoordinatePOSrange positioning FFDs Address & Target devices lists Pre- determined processing time(T) Power Control

93. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 93 Design Parameters (1) Motivation: – Flexible waveform – Simple – Compatible with multiple coherent/non-coherent receiver schemes Large Bandwidth (+) Higher transmit power (+) improved time resolution (-) Increased design complexity (-) Less stringent requirements on out of band interference filtering  Signal BW of 500 MHz - 2 GHz in Upper bands Signal BW of 700 MHz in 0 to 960 MHz Lower band (low band) Long Pulse Repetition Period (+) more energy per pulse (easier to detect single pulse) (+) Lower inter-pulse interference due to channel delay spread (-) Higher peak voltage requirements at transmitter (-) Longer acquisition time  Frame duration between 40ns (first realization) and 125ns (second realizations). Higher values for the frame duration have been mentioned. Further discussions are required to fix the values

94. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 94 Simple modulation schemes: BPPM combined with Transmitted Reference Channelization : Coherent schemes: Use of TH codes and polarity codes Non-coherent schemes: Use of TH codes (polarity codes for spectrum smoothing only) Long TH code length (+) higher processing gain, robustness to SOP operation (-) Lower bit-rate (-) Longer acquisition time, shorter frame size (synch. phase)  TH code length 8 or 16 TH code : binary position (delay of 0 or τ Δ ), bi-phase For first realization, higher-order TH with shorter chip duration (multiples of 2ns) can be used. This is under discussion Design Parameters (2)

95. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 95 Transmission Basic idea: use modulation scheme that allows coherent, differentially coherent, and incoherent reception Combine BPPM with more sophisticated TR scheme – Non-coherent receiver sees BPPM with pulse stream per bit – More sophisticated receiver sees BPPM (1 bit) plus bits carried in more sophisticated modulation scheme (e.g. extended TR) Advantages: – Coherent, differential and non-coherent receiver may coexist – reference can be used for synch and threshold estimation Concept can be generalized to N-ary TR system

96. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 96 Waveform Design Coexistence of coherent and non-coherent architectures Combine BPPM with BPSK Divide each symbol into two 125 ns BPPM slots (250 ns symbol) In either slot transmit a signal that can be received with a variety of receivers: differentially coherent or coherent receivers. Non-coherent receivers just look for energy in the early or late slots to decode the bit. Other receivers understand the fine structure of the signal.

97. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 97 Waveform Design Two possible realizations: – The whole symbol (consisting of N_f frames) is BPPM-modulated. – Have a 2-ary time hopping code, so that each frame has BPPM according to TH code

98. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 98 First Realization

99. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 99 Second Realization Ts « 11 » « 01 » 2-PPM + TR base M = 2 (with two bits/symbol) One bit/symbol also Possible !!! « 10 » « 00 » (coherent decoding possible) 2-PPM + 16 chips 2-ary TH code This is a time-hopping that can be exploited by non-coherent receiver Time hopping code is (2,2) code of length 8 or 16 Effectively 28 or 216 codes to select for channelization for non-coherent scheme

100. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 100 Time Hopping Impulse Radio (TH-IR) - Principle TsTs TcTc TfTf +1 Each symbol represented by sequence of very short pulses (see also Win & Scholtz 2000) Each user uses different sequence (Multiple access capability) Bandwidth mostly determined by pulse shape

101. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 101 Mitigation of peak voltage through multi pulses Tf=PPI IS « EQUIVALENT » TO ppV = peak-to-peak voltage ppV/2 M = 4 M = 1 Tf=PPI ppV/sqrt(2) M = 2

102. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 102 Coexistence of Different Receiver Architectures Want waveform that allows TR reception without penalizing coherent reception That is achieved by special encoding and waveform shaping within each frame. Does not affect the co-existence of coherent/non- coherent receivers

103. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 103 Basic Properties Use of Doublets with memory from previous bit. (Encoding of reference pulse with previous bit) – Agreed on 20ns separation between pulses – Extensible to higher order TR for either reducing the penalty in transmitting the reference pulse or increasing the bit rate? – Also allows the use of multi-DOUBLET

104. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 104 TsTs Differential Encoding of Bits +1 -1 +1 -1 +1 -1 -1 -1 +1 +1 -1 -1 0 0 1 1 0 0 1 b0b0 b4b4 b3b3 b2b2 b1b1 b5b5 b -1 Tx Bits Reference Polarity Note: This slide is meant to describe the encoding of data on the reference pulse and data pulse in the basic modulation format. For simplicity we have omitted the multipulse/multiframes per symbol structure.

105. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 105 Total Modulation Scheme (First Realization) THE KEY SLIDE OF THE PROPOSAL: this is the modulation format that allows Coherent, differentially coherent, and non-coherent demodulation at once

106. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 106 Higher-order modulation TH Pattern TH Code 1,1 1,1 0,1 0,0 1,0 0,1 Data 1,1 1,1 1,1 1,1 1,1 0,0 Pulse Shift, polarity invert τ Δ + τ delay Enhanced Mode 1 D « 1 1 » « 1 0 » DD τ delay + τ Δ τΔτΔ τ delay τ Δ + τ delay τ delay τΔτΔ τ Δ + τ delay Basic Mode (as seen by non-coherent) « 1 » τ delay + τ Δ D DD

107. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 107 Comments on Transmitted Signal Frame period for solution 2 is T frame = (N p * D) + τ Δ + τ delay – Τ delay is some allowance for channel delay spread Frame period could be dynamic modified dependant on – the estimated channel delay spread or – ability of receiver to cope with delay spread Symbol period is length of the TH code x T frame – Upper Band Nominally 250 ns x 16 = 4 µs – Lower Band Nominally 500 ns x 8 = 4 µs Realistic Receiver structures exist for multi-pulse TR schemes (see back-up slides)

108. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 108 BER Performance in AWGN Channel

109. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 109 Antenna Practicality Bandwidth: 3 GHz-10 GHz Form factor Omni-directional y x z 7 mm ground plane Ø 80 mm antenna hat Ø 24 mm  

110. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 110 Mobile (x m,y m ) Anchor 1 (x A1,y A1 ) Anchor 2 (x A2,y A2 ) Anchor 3 (x A3,y A3 ) Positioning from TDOA 3 anchors with known positions (at least) are required to find a 2D-position from a couple of TDOAs Measurements Estimated Position Specific Positioning Algorithms

111. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 111 TR BPPM Scheme Comparison

112. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 112 Assumptions and Notes Results are theoretical calculations Assumes ideal ”impulse” UWB pulses in AWGN channel Different TR-BBP options are considered with different number of pulses per pulse train Multipath fading simulations can be performed to back up theory

113. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 113 Pulse repetition structures TR BPPM with doublets (Scheme 1)

114. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 114 Pulse repetition structures TR BPPM single reference (Scheme 2)

115. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 115 Pulse repetition structures Auto Correlation BPPM with doublets (Scheme 3)

116. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 116 Pulse repetition structures Auto Correlation BPPM single reference (Scheme 4)

117. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 117 Pulse repetition structures Auto Correlation BPPM alternate ( Scheme 5)

118. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 118 Parameters PPI slot - slot inside each TH chip containing a burst of pulses including reference pulses (ref. slides from Laurent / CEA) N p represents the number of pulses in each PPI slot The energy E per PPI slot is kept constant The pulse energy E p = E/N p TW represent the time-bandwidth product

119. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 119 E p /N 0 degradation versus number of pulses per pulse train

120. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 120 E p /N 0 degradation versus Time/Bandwidth product

121. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 121 E p /N 0 degradation versus number of pulses per pulse train

122. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 122 Conclusions Scheme 5 - “AC Alternate” performs better then all the other pulse repetition structures. AC generally performs better than TR “AC alternate” and “AC with doublets” have the advantage of requiring only a single delay line. Scheme 5 - “AC Alternate”, was proposed at Monterey meeting in January. Criticism was given based on ”accumulated noise” in noise- cross-noise-cross-noise... Products”. Seems to outperform other schemes with simple analysis Also more readily implementable since fixed delay line can be used.

123. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 123 Channel / Delay Estimation Coherent Approach

124. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 124 Channel / Delay Estimation Coherent Approach Swept delay correlator Principle: estimating only one channel sample per symbol. Similar concept as STDCC channel sounder of Cox (1973). Sampler, AD converter operating at SYMBOL rate (1.2 Msamples/s) Requires longer training sequence Two-step procedure for estimating coefficients: – With lower accuracy: estimate at which taps energy is significant – With higher accuracy: determine tap weights “Silence periods”: for estimation of interference

125. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 125 Optimal Energy-Threshold Analysis (CM-1) Optimal normalized threshold (normalized with respect to the difference between the maximum and minimum energy blocks) changes with E b /N 0 and block size. Smaller thresholds are required in general at high E b /N 0, while larger thresholds at lower SNR values MAE Mean Absolute Error in detecting leading energy block with simple threshold crossing (1000 channel realizations) E b /N 0 : { 8 --- 26dB}

126. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 126 Proposed RAKE -- Coherent Receiver Rake Receiver Finger Np Demultiplexer Rake Receiver Finger 2 Rake Receiver Finger 1 Summer Channel Estimation Convolutional Decoder Data Sink Sequence Detector Addition of Sequence Detector – Proposed modulation may be viewed as having memory of length 2 Main component of Rake finger: pulse generator A/D converter: 3-bit, operating at symbol rate No adjustable delay elements required

127. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 127 Proposed Transmitted Reference Receiver – Differentially Coherent TdTd Matched Filter Convolutional Decoder Addition of Matched Filter prior to delay and correlate operations improves output signal to noise ratio and reduces noise-noise cross terms SNR of decision statistic

128. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 128 Band Matched LNALNA BPF Tracking Threshol ds setting Tracking DumpLatchDumpLatch RAZ DUMP ControlledIntegrator ADC BPPM Demodulation branch RAZ Differentially-Coherent/Non-Coherent Receiver Architecture Basic Mode and Enhanced Mode 1 x 2 r(t) Recyle this branch for Enhanced Data Rate Modes DelayDelay TR Demodulation branch DumpLatchDumpLatch ADC ControlledIntegrator BPPM Synch Trigger TR Energy Analyzer Block index for acquisition reference Leading-edge refinement search Range info Ranging branch

129. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 129 Band Matched LNALNA BPF De-spreading TH Codes r(t) TH Sequence Matched Filter Bit Demodulation Band Matched LNALNA BPF r(t) TH Sequence Matched Filter Bit Demodulation Case I - Coherent TH despreading ADC ADC b(t) soft info Case II – Non-coherent / differential TH despreading

130. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 130 Bandwidth Usage – 2GHz option (2/4) 0.96 3.1 5.1 6.0 8.0 8.1 10.1 GHz ISM Band Upper Band 1 Upper Band 2 Upper Band 3 Lower band ISM Band

131. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 131 Bandwidth Usage -500 MHz Option (3/4) 0.96 3.1 5.1 6.0 8.0 8.1 10.1 GHz ISM Band Lower band ISM Band Upper Bands 1 - 4 Upper Bands 5 - 12

132. Mar. 2005 doc.: IEEE 802.15-05-0158-00-004a Slide 132 Bandwidth Usage –Variable Option (4/4) 0.96 3.1 5.1 6.0 8.0 8.1 10.1 GHz ISM Band Lower band ISM Band Upper Bands 1 - 4 Upper Bands 5 - 12