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Modeling and Design for Beyond-the-Die Power Integrity Yiyu Shi, ECE Dept., Missouri Univ. of Science and Technology (formerly University of Missouri-Rolla)

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Presentation on theme: "Modeling and Design for Beyond-the-Die Power Integrity Yiyu Shi, ECE Dept., Missouri Univ. of Science and Technology (formerly University of Missouri-Rolla)"— Presentation transcript:

1 Modeling and Design for Beyond-the-Die Power Integrity Yiyu Shi, ECE Dept., Missouri Univ. of Science and Technology (formerly University of Missouri-Rolla) Lei He, EE Dept., Univ. of California, Los Angeles

2 2 ICCAD’10 Importance of Power Integrity ● Power supply noise is a major threat for circuit reliability in 45nm and beyond – reduces noise margin of digital circuits – shifts the operating point of analog circuits – decreases the effective driving strength of the gates – causes output signal distortion (e.g. jitters) impairing signal integrity

3 3 ICCAD’10 Simultaneous Switching Noise (SSN) ● a major threat to the power integrity ● occurs due to a very large amount of instantaneous P/G current from simultaneously switching gates ● mainly inductive ● most significantly observed around the output pads of the chip – large I/O buffers – clock synchronized I/O – Large inductance in package

4 4 ICCAD’10 Power Delivery System ● three distinct peaks – ~kHz (power regulator/board) – ~MHz (package/board) – ~100MHz (chip/package) ● significant noise near the largest peak ● need accurate models to capture it How to estimate SSN for a given design, and how to effectively suppress it? Shi et al, “stochastic current prediction enabled frequency actuator for runtime resonance noise reduction”, ASPDAC’10

5 5 ICCAD’10 Outline  Modeling  Chip Models  Package and Board Models  Design  I/O planning and placement  Decap Allocation  Layer Stacking and P/G Plane Stapling

6 6 ICCAD’10 impossible to put detailed models of chip, package and board together for the simulation due to the high complexity need some simplified models that preserve only necessary information for the simulation but how? Models for Chip/Package/Board

7 7 ICCAD’10 Transistor Models ● most accurate ● require detailed info about the circuit and process parameters, which vendors are reluctant to provide ● not all simulators are fully compatible ● slow simulation speed ● no convergence guarantee

8 8 ICCAD’10 Current Source Model ● model the chip I/O as a time variant/invariant current source with parasitic R and C ↑ ● the non-linearity of the I/O buffer is ignored => negative feedback effect is ignored voltage drop ↓ switching current ↓

9 9 ICCAD’10 I/O Buffer Information Specification a universal standard for describing the buffers using data in ASCII text format – Not really models – just behavioral data to be used by simulators started in the early 90s to promote tool- independent I/O models for system-level signal integrity work IBIS 3.2 is standardized: ANSI/EIA-656-A and IEC 62014-1 IBIS 4.1 incorporates links to VHDL-AMS and Verilog-AMS IBIS Models Wiki: IBIS is a group of long- legged wading birds in the family Threskiornithidae

10 10 ICCAD’10 Elements of an IBIS Model

11 11 ICCAD’10 Pros and Cons of IBIS Models Pros – simulate much faster than SPICE model – protect circuit and process intellectual properties – easy portability and guaranteed convergence Cons – extrapolation required when load is out of the range (inaccurate) – model regeneration required when the package parasitics change – cannot capture the dynamic characteristics as the data relies primarily on static characteristics ● Only good when the I/O speed is not high!

12 12 ICCAD’10 use radial basis function (RBF) to represent the I/O dynamic behavior – accurate – intractable for complex driver circuits with multiple ports use spline functions with a finite time difference approximation – include the previous time instances of the buffer output voltage/current – cannot be extended to highly nonlinear buffers Other Models for Chip I/O…

13 13 ICCAD’10 Lumped/Distributed Models for Package/Board ● Lumped models – use simple geometry with a few RLC elements (e.g. π equivalent circuit) – efficient but lack accuracy – should only be used for low performance/speed design ● Distributed models – run parasitic extraction – huge number of RLC elements – model reduction or other simplification techniques are needed to reduce complexity – High computational cost

14 14 ICCAD’10 measured by sending a single frequency signal into the network and detecting the exit waveform at each port frequency dependent, load dependent can be obtained using a 3D full-wave EM simulator such as HFSS or using vector network analyzer (VNA) By sweeping over a wide frequency range, they can reveal frequency-dependent characteristics (e.g. skin effect and dielectric conductance effect) S-Parameters 101

15 15 ICCAD’10 Simulation with S Parameters ● simulated directly using convolution-based methods in frequency domain ● or synthesize an RLC circuit from S-parameters in time domain – create a circuit template with a certain topology – convert the measured S parameters to Y or Z parameters – matching the Y/Z parameters of the template and the measured Y/Z parameters to determine the element values in the template ● put some stringent requirements on S-parameters – passivity (and thus stability and causality) – but hard to satisfy while maintaining accuracy

16 16 ICCAD’10 Importance of Co-Simulation ● A differential pair from chip to package to board Comparison of the S11 parameter and the power supply voltage from chip, package and board co-simulation and these from separate simulation.

17 17 ICCAD’10 Frequency model for circuit I/O Frequency model for circuit I/O Possible Co-Simulation Flows S parameters for package/board S parameters for package/board Inverse Transform IBIS model for circuit I/O IBIS model for circuit I/O Ckt realization of S parameters for package/board Ckt realization of S parameters for package/board Frequency domain Time domain

18 18 ICCAD’10 Outline  Modeling  Chip Models  Package and Board Models  Design  I/O planning and placement  Decap Allocation  Layer Stacking and P/G Plane Stapling

19 19 ICCAD’10 Flip-chip design Assign pins and pads to signals and power/ground supply I/O Planning and Placement Xiong et al, ““constraint driven I/O planning and placement for chip-package co-design”, ASPDAC’06

20 20 ICCAD’10 Rule #1 ● separate the P/G pins and pads for analog and digital signals whenever possible ● minimize the digital noise coupled to the analog portion

21 21 ICCAD’10 ● SSN is negatively correlated to the ratio of # of P/G pads/pins to # of signal pads/pins ● insert as many P/G pads and pins as possible ● total inductance ↓ (parallel connection) ● the slew of the SSN v.s. # of switching I/O buffers curve ↓ Rule #2 obtained from Q3D extraction

22 22 ICCAD’10 Decoupling Capacitor Allocation ● short power and ground planes at high frequencies to control voltage fluctuations ● discrete passive components with a given capacitance with parasitic resistance and inductance ● Determine the optimal decap allocation strategy

23 23 ICCAD’10 Decap Allocation ● considering the congestion from signal and power routing, decaps can be inserted only at selected slots ● usually minimize the total decap cost subject to power integrity and congestion constraints Before decap allocation After decap allocation Hao et al, “Off-chip decoupling capacitor allocation for chip package co-design,” DAC’07 Chen et al, “Noise-driven in-package decoupling capacitance insertion,” ISPD’06

24 24 ICCAD’10 Layer Stacking and P/G Plane Stapling ● in high performance flip-chip package, multiple layers are typically used for P/G planes and signal routing ● Determine the number of layers and the locations of the vias to staple them

25 25 ICCAD’10 Determine the Number of Layers ● The # of layers depends on – cost – the # of the signals to be routed – the cross-talk constraints of these signals – the #of voltage domains, which constraints  the # of power plane layers  how a layer should be partitioned and shared by multiple voltage domains ● usually multiple P/G planes are used to keep the power supply noise low and to shield the signal routing layer – If affordable, shield every routing layer by alternated power/ground planes in between

26 26 ICCAD’10 Stapling Rules ● the resonance frequency ↑ as the number of vias ↑ ● the locations of the vias do not have a significant impact on the resonance frequency. Instead, they change the inductance of the package. ● a centered via distribution always has a lower inductance than a uniform via distribution  Always cluster P/G vias for each power domain! centered uniform Zhao et al, “Effects of power/ground via distribution on the power/ground performance of C4/BGA packages,” epep’98.

27 27 ICCAD’10 Conclusions ● Power integrity has become an increasingly important design consideration for circuit designs in 45nm technology and beyond ● We have provided an overview of power-integrity driven modeling and design issues for beyond the die ● We have discussed – background of simultaneous switching noise (SSN) and its significance to the circuit designers – various models of different accuracy and complexity for the board, package and chip – different design techniques to suppress SSN

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